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NCP1522 3.0 MHz, 600 mA, High-Efficiency, Low Quiescent Current, Adjustable Output Voltage Step-Down Converter
The NCP1522 step-down PWM DC-DC converter is optimized for portable applications powered from one cell Li-ion or three cell Alkaline/NiCd/NiMH batteries. The device is available in an adjustable output voltage from 0.9 V to 3.3 V. It uses synchronous rectification to increase efficiency and reduce external part count. The device also has a built-in 3.0 MHz (nominal) oscillator which reduces component size by allowing a small inductor and capacitors. Automatic switching PWM/PFM mode offers improved system efficiency. Finally, it includes an integrated soft-start, cycle-by-cycle current limiting, and thermal shutdown protection. The NCP1522 is available in a space saving, low profile TSOP5 package.
Features
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5 5 1 TSOP-5 ASN SUFFIX CASE 483 DBRAYWG G 1
* 93.8% of Efficiency for 3.3 V Output and 4.5 V Input and 120 mA * * * * * * * * * * * * * * * *
Load Current Sources up to 600 mA 3.0 MHz Switching Frequency Adjustable Output Voltage from 0.9 V to 3.3 V 60 mA Quiescent Current (Typ) Synchronous Rectification for Higher Efficiency 2.7 V to 5.5 V Input Voltage Range Thermal Limit Protection Shutdown Current Consumption of 0.3 mA Short Circuit Protection This is a Pb-Free Device Cellular Phones, Smart Phones and PDAs MP3 Players and Portable Audio Systems Wireless and DSL Modems Portable Equipment USB Powered Devices Digital Still/Video Cameras
A = Assembly Location Y = Year W = Work Week G = Pb-Free Package (Note: Microdot may be in either location)
PIN CONNECTIONS
VIN GND EN 1 2 3 (Top View) 4 FB 5 LX
ORDERING INFORMATION
Device NCP1522ASNT1G Package Shipping
Typical Applications
TSOP-5 3000/T ape & Reel (Pb-Free)
For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging Specification Brochure, BRD8011/D.
VIN CIN
L 1 2 VIN GND EN FB 4 LX 5 COUT
VOUT
R1 OFF ON 3
Cff
R2
Figure 1. Typical Application
(c) Semiconductor Components Industries, LLC, 2006
1
August, 2006 - Rev. 3
Publication Order Number: NCP1522/D
NCP1522
100
90
Eff (%)
80
70 Vout = 3.3 V Vin = 4.5 V TA = 25C
60
50 0 100 200 300 Iout (mA) 400 500 600
Figure 2. Efficiency vs. Output Current
Q1 Vbattery Q2 VIN 1 PWM/BURST CONTROL LX 5 2.2 mH
4.7 mF
4.7 mF
GND 2
ILIMIT
R1
18 pF
Enable
EN 3
LOGIC CONTROL & THERMAL SHUTDOWN REFERENCE VOLTAGE
FB 4
R2
Figure 3. Simplified Block Diagram
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PIN FUNCTION DESCRIPTION
Pin No. 1 2 3 4 5 Symbol VIN GND EN FB LX Function Analog Input Analog/Power Ground Digital Input Analog Input Analog Output Description Power Supply Input for Analog VCC. Ground connection for the NFET Power Stage and the Analog Sections of the IC. Enable for Switching Regulator. This pin is active high. Do not float this pin. Feedback voltage from the output of the power supply. This is the input to the error amplifier. Connection from Power MOSFETs to the Inductor. For one option, an output discharge circuit sinks current from this pin.
MAXIMUM RATINGS
Rating Minimum Voltage All Pins Maximum Voltage All Pins (Note 1) Maximum Voltage Enable, FB, LX Thermal Resistance, Junction -to-Air Operating Ambient Temperature Range Storage Temperature Range Junction Operating Temperature Latch-up Current Maximum Rating (TA = 85C) (Note 2) ESD Withstand Voltage (Note 3) Human Body Model Machine Model Symbol Vmin Vmax Vmax RqJA TA Tstg Tj Lu Vesd 2.0 200 kV V Value -0.3 7.0 VIN + 0.3 200 -40 to 85 -55 to 150 -40 to 125 +/-100 Unit V V V _C/W _C _C _C mA
Stresses exceeding Maximum Ratings may damage the device. Maximum Ratings are stress ratings only. Functional operation above the Recommended Operating Conditions is not implied. Extended exposure to stresses above the Recommended Operating Conditions may affect device reliability. 1. According to JEDEC standard JESD22-A108B. 2. Latchup current maximum rating per JEDEC standard: JESD78. 3. This device series contains ESD protection and exceeds the following tests: Human Body Model (HBM) per JEDEC standard: JESD22-A114. Machine Model (MM) per JEDEC standard: JESD22-A115.
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ELECTRICAL CHARACTERISTICS (Typical values are referenced to TA = +25C, Min and Max values are referenced -40C to +85C ambient temperature, unless otherwise noted, operating conditions VIN = 3.6 V, VOUT = 1.8 V, unless otherwise noted.)
Characteristic Input Voltage Range Undervoltage Lockout (VIN Falling) Quiescent Current (PFM No Load) Standby Current, EN Low Oscillator Frequency Peak Inductor Current Feedback Reference Voltage FB Pin Tolerance Reference Voltage Line Regulation Output Voltage Accuracy (Note 4) Minimum Output Voltage Maximum Output Voltage Output Voltage Line Regulation (Vin = 2.7-5.5) Io = 200 mA Voltage Load Regulation (IO = 200 mA to 300 mA) (IO = 200 mA to 600 mA) Load Transient Response (300 mA to 600 mA Load Step, Trise 1.0 ms) Duty Cycle P-Ch On-Resistance N-Ch On-Resistance P-Ch Leakage Current N-Ch Leakage Current Enable Pin High Enable Pin Low EN << H >> Input Current, EN = 3.6 V Soft-Start Time Thermal Shutdown Threshold Thermal Shutdown Hysteresis Symbol VIN VUVLO Iq Istb Fosc ILIM Vref VFBtol DVFB VOUT VOUT VOUT DVOUT VLOADREG - - VOUT - RLxH RLxL ILeakH ILeakL VENH VENL IENH Tstart TSD TSDH - - - - - - 1.2 - - - - - 0.0005 0.001 35 - 300 300 0.05 0.01 - - 2.0 350 160 25 - - - 100 - - - - - 0.4 - 500 - - %/mA %/mA mV % mW mW mA mA V V mA ms C C Min 2.7 2.3 - - 2.400 - - -3.0 - -3% - - - Typ - 2.5 60 0.3 3.0 1200 0.6 - 0.1 Vnom 0.9 3.3 0.1 Max 5.5 2.6 95 1.2 3.600 - - 3.0 - +3% - - - Unit V V mA mA MHz mA V % % V V V %
4. The overall output voltage tolerance depends upon the accuracy of the external resistor (R1, R2).
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100 90 QUIESCENT CURRENT (mA) 80 70 60 50 40 30 20 10 0 2.7 3.2 3.7 4.2 4.7 EN = VIN IOUT = 0 mA 5.2 5.7 QUIESCENT CURRENT (mA) 100 90 80 70 60 50 40 30 20 10 0 -40 -20 0 20 40 60 80 100 VIN = 5.5 V VIN = 2.7 V
VIN, INPUT VOLTAGE (V)
TEMPERATURE (C)
Figure 4. Quiescent Current vs. Supply Voltage
Figure 5. Quiescent Current vs. Temperature
1.0 EN = 0 V SHUTDOWN CURRENT (mA) 0.8 IOUT = 0 mA EFFICIENCY (%)
100 95 90 85 80 75 70 3.2 3.7 4.2 4.7 0 100 200 300 400 500 600 VIN, INPUT VOLTAGE (V) IOUT, OUTPUT CURRENT (mA) TA = 85C TA = -40C TA = 25C
0.6
0.4
0.2
0 2.7
Figure 6. Shutdown Current vs. Supply Voltage
Figure 7. Efficiency vs. Output Current (VOUT = 1.8 V, VIN = 3.6 V)
100
100
90 EFFICIENCY (%) EFFICIENCY (%) TA = -40C 80 TA = 25C 90 TA = 25C 80
TA = -40C
TA = 85C
70
60 TA = 85C 50 0 100 200 300 400 500 600 IOUT, OUTPUT CURRENT (mA) 70 0 100 200 300 400 500 600 IOUT, OUTPUT CURRENT (mA)
Figure 8. Efficiency vs. Output Current (VOUT = 0.9 V, VIN = 3.6 V)
Figure 9. Efficiency vs. Output Current (VOUT = 3.3 V, VIN = 4.5 V)
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100 90 EFFICIENCY (%) 80 70 60 50 40 30 0 100 200 300 400 500 600 IOUT, OUTPUT CURRENT (mA) VOUT = 0.9 V VOUT = 1.8 V VOUT = 3.3 V FREQUENCY (MHz) 3.6 3.4 3.2 IOUT = 300 mA 3.0 2.8 2.6 2.4 2.7 IOUT = 600 mA
3.2
3.7
4.2
4.7
5.2
5.7
VIN, INPUT VOLTAGE (V)
Figure 10. Efficiency vs. Output Current (VIN = 4.0 V)
3.6 3.4 FREQUENCY (MHz) 3.2 3.0 2.8 2.6 IOUT = 300 mA 2.4 -40 -20 0 20 40 60 80 100 VIN = 3.6 V 3.0 2.5 2.0 1.5 1.0 0.5 0.0 -0.5 -1.0 -1.5 -2.0 -2.5 -3.0 0
Figure 11. Frequency vs. Input Voltage
VOUT = 0.9 V VOUT = 1.8 V
VIN = 5.5 V
LOAD REGULATION (%)
VOUT = 3.3 V
100
200
300
400
500
600
700
TEMPERATURE (C)
IOUT, OUTPUT CURRENT (mA)
Figure 12. Frequency vs. Temperature
Figure 13. Load Regulation
2.0
300 VOUT = 1.8 V 250 200 150 100 50 0 2.7 TA = 25C
1.5
1.0
0.5
0.0 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 VIN, ENABLE INPUT VOLTAGE (V)
OUTPUT CURRENT (mA)
OUTPUT VOLTAGE (V)
3.2
3.7
4.2
4.7
5.2
5.7
VIN, INPUT VOLTAGE (V)
Figure 14. Output Voltage vs. Enable Input Pin Voltage
Figure 15. PFM/PWM Threshold vs. Input Voltage
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2.0 1.5 OUTPUT VOLTAGE (%) 1.0 0.5 0.0 -0.5 -1.0 -1.5 VIN = 3.6 V -2.0 -50 0 50 TEMPERATURE (C) 100 150 -2.0 -50 IOUT = 300 mA OUTPUT VOLTAGE (%) IOUT = 100 mA 2.0 1.5 1.0 0.5 0.0 -0.5 -1.0 -1.5 VIN = 3.6 V 0 50 TEMPERATURE (C) 100 150 IOUT = 100 mA IOUT = 300 mA
IOUT = 600 mA
IOUT = 600 mA
Figure 16. Output Voltage Accuracy (VOUT = 0.9 V)
Figure 17. Output Voltage Accuracy (VOUT = 1.8 V)
2.0 1.5 OUTPUT VOLTAGE (%) 1.0 0.5 IOUT = 100 mA 0.0 -0.5 -1.0 -1.5 VIN = 4.0 V -2.0 -50 0 50 TEMPERATURE (C) 100 150 IOUT = 600 mA IOUT = 300 mA
Figure 18. Output Voltage Accuracy (VOUT = 3.3 V)
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IOUT 200 mA/Div
IOUT 200 mA/Div
VOUT 20 mV/Div 10 ms/Div
VOUT 20 mV/Div 10 ms/Div
Figure 19. Load Transient Response in PWM Operation (VIN = 3.6 V)
Figure 20. Load Transient Response in PWM Operation (VIN = 3.6 V)
2.5 ms/Div EN 2 V/Div ILX 500 mA/Div VOUT 500 mV/Div VOUT 100 ms/Div 500 mV/Div
Figure 21. Soft Start Time (VIN = 3.6 V)
Figure 22. Short Circuit Protection (VIN = 3.6 V)
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NCP1522
OPERATION DESCRIPTION
Overview
The NCP1522 uses a constant frequency, voltage mode step-down architecture. Both the main (P-Channel MOSFET) and synchronous (N-Channel MOSFET) switches are internal. It delivers a constant voltage from either a single Li-Ion or three cell NiMH/NiCd battery to portable devices such as cell phones and PDA. The output voltage is set by external resistor divider. The NCP1522 sources at least 600 mA depending on external components chosen. The NCP1522 works with two modes of operation; PWM depending on the current required. The device operates in PWM/PFM mode at load currents of approximately 80 mA or higher, having voltage tolerance of "3% with 90% efficiency or better. Lighter load currents cause the device to automatically switch into PFM mode for reduced current consumption (IQ = 60 mA typ) and extended battery life. Additional features include soft-start, undervoltage protection, current overload protection, and thermal shutdown protection. As shown in Figure 1, only six external components are required for implementation. The part uses an internal reference voltage of 0.6 V. It is recommended to keep the part in shutdown until the input voltage is 2.7 V or higher.
PWM Operating Mode
125 ns/div
Figure 23. PWM Switching Waveform (Vin = 3.6 V, Vout = 1.8 V, Iout = 300 mA) PFM Operating Mode
In this mode, the output voltage of the NCP1522 is regulated by modulating the on-time pulse width of the main switch Q1 at a fixed frequency of 3.0 MHz. The switching of the PMOS Q1 is controlled by a flip-flop driven by the internal oscillator and a comparator that compares the error signal from an error amplifier with the PWM ramp. At the beginning of each cycle, the main switch Q1 is turned ON by the rising edge of the internal oscillator clock. The inductor current ramps up until the sum of the current sense signal and compensation ramp becomes higher than the error voltage amplifier. Once this has occurred, the PWM comparator resets the flip-flop, Q1 is turned OFF and the synchronous switch Q2 is turned ON. Q2 replaces the external Schottky diode to reduce the conduction loss and improve the efficiency. To avoid overall power loss, a certain amount of dead time is introduced to ensure Q1 is completely turned OFF before Q2 is being turned ON.
Under light load conditions, the NCP1522 enters in low current PFM mode operation to reduce power consumption. The output regulation is implemented by pulse frequency modulation. If the output voltage drops below the threshold of PFM comparator (typically Vnom-2%), a new cycle will be initiated by the PFM comparator to turn on the switch Q1. Q1 remains ON until the peak inductor current reaches 200 mA (nom). Then ILIM comparator goes high to switch off Q1. After a short dead time delay, switch rectifier Q2 is turned ON. The negative current detector (NCD) will detect when the inductor current drops below zero and sends the signal to turn off Q2. The output voltage continues to decrease through discharging the output capacitor. When the output voltage falls below the threshold of the PFM comparator, a new cycle starts immediately.
5 ms/div
Figure 24. PFM Mode Switching Waveform (Vin = 3.6 V, Vout = 1.8 V, Iout = 30 mA)
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Cycle-by-Cycle Current Limitation
From the block diagram (Figure 3), an ILIM comparator is used to realize cycle-by-cycle current limit protection. The comparator compares the LX pin voltage with the reference voltage, which is biased by a constant current. If the inductor current reaches the limit, the ILIM comparator detects the LX voltage falling below the reference voltage and releases the signal to turn off the switch Q1. The cycle-by-cycle current limit is set at 1200 mA (nom).
Short Circuit Protection
consumption will be 0.3 mA (typical value). Applying a voltage above 1.2 V to EN pin will enable the device for normal operation. The device will go through soft-start to normal operation, however, the EN pin should be tied low while the input voltage on VIN pin is rising up.
Thermal Shutdown
When the output is shorted to ground, the device limits the inductor current. The duty-cycle is minimum and the consumption on the input line is 300 mA (Typ). When the short circuit condition is removed, the device returns to the normal mode of operation.
Soft-Start
Internal Thermal Shutdown circuitry is provided to protect the integrated circuit in the event that the maximum junction temperature is exceeded. If the junction temperature exceeds 160_C, the device shuts down. In this mode switch Q1 and Q2 and the control circuits are all turned off. The device restarts in soft-start after the temperature drops below 135_C. This feature is provided to prevent catastrophic failures from accidental device overheating and it is not intended as a substitute for proper heatsinking.
Low Dropout Operation
The NCP1522 uses soft-start (300 ms Typ) to limit the inrush current when the device is initially enabled. Soft-start is implemented by gradually increasing the reference voltage until it reaches the full reference voltage. During startup, a pulsed current source charges the internal soft-start capacitor to provide gradually increasing reference voltage. When the voltage across the capacitor ramps up to the nominal reference voltage, the pulsed current source will be switched off and the reference voltage will switch to the regular reference voltage.
Shutdown Mode
The NCP1522 offers a low input to output voltage difference. The NCP1522 can operate at 100% duty cycle. In this mode the PMOS (Q1) switches completely on. The minimum input voltage to maintain regulation can be calculated as:
VIN(min) + VOUT(max) ) (IOUT (RDS(on) ) RINDUCTOR))
(eq. 1)
When the EN pin has a voltage applied of less than 0.4 V, the NCP1522 will be disabled. In shutdown mode, the internal reference, oscillator and most of the control circuitries are turned off. Therefore, the typical current
* * * *
VOUT: Output Voltage (Volts) IOUT: Max Output Current RDS(on): P-Channel Switch RDS(on) RINDUCTOR: Inductor Resistance (DCR)
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APPLICATION INFORMATION
Output Voltage Selection
The corner frequency is given by:
fc + 1 2p L COUT + 1 2p 2.2 mH 4.7 mF + 49.5 kHz
(eq. 3)
The output voltage is programmed through an external resistor divider connected from VOUT to FB then to GND. For low power consumption and noise immunity, the resistor from FB to GND (R2) should be in the [100 k-600 k] range. If R2 is 200 k given the VFB is 0.6 V, the current through the divider will be 3.0 mA. The formula below gives the value of VOUT, given the desired R1 and the R1 value:
VOUT + VFB (1 ) R1) R2
(eq. 2)
* * * *
VOUT: Output Voltage (Volts) VFB: Feedback Voltage = 0.6 V R1: Feedback Resistor from VOUT to FB R2: Feedback Resistor from FB to GND
The device is intended to operate with inductance between 1.0 mH and maximum of 4.7 mH. If the corner frequency is moved, it is recommended to check the loop stability depending on the output ripple voltage accepted and output current required. For lower frequency, the stability will be increased; a larger output capacitor value could be chosen without critical effect on the system. On the other hand, a smaller capacitor value increases the corner frequency and it should be critical for the system stability. Take care to check the loop stability. The phase margin is usually higher than 45.
Table 2. L-C Filter Example
Inductance (L) 1.0 2.2 4.7 Output Capacitor (Cout) 10 4.7 2.2
Input Capacitor Selection
In PWM operating mode, the input current is pulsating with large switching noise. Using an input bypass capacitor can reduce the peak current transients drawn from the input supply source, thereby reducing switching noise significantly. The capacitance needed for the input bypass capacitor depends on the source impedance of the input supply. The maximum RMS current occurs at 50% duty cycle with maximum output current, which is IO, max/2. For NCP1522, a low profile, low ESR ceramic capacitor of 4.7 mF should be used for most of the cases. For effective bypass results, the input capacitor should be placed as close as possible to the VIN pin.
Table 1. List of Input Capacitor
Murata GRM188R60J475KE GRM21BR71C475KA Taiyo Yuden TDK JMK212BY475MG C2012X5ROJ475KB C1632X5ROJ475KT
mH mH mH
mF mF mF
Inductor Selection
The inductor parameters directly related to device performances are saturation current and DC resistance and inductance value. The inductor ripple current (AIL) decreases with higher inductance:
V V DIL + OUT 1- OUT L fSW VIN
(eq. 4)
DIL peak to peak inductor ripple current L inductor value fSW switching frequency The saturation current of the inductor should be rated higher than the maximum load current plus half the ripple current:
DI IL(MAX) + IO(MAX) ) L 2
(eq. 5)
Output L-C Filter Design Considerations
The NCP1522 is built in 3.0 MHz frequency and uses voltage mode architecture. The correct selection of the output filter ensures good stability and fast transient response. Due to the nature of the buck converter, the output L-C filter must be selected to work with internal compensation. For NCP1522, the internal compensation is internally fixed and it is optimized for an output filter of L = 2.2 mH and COUT = 4.7 mF.
IL(MAX) Maximum Inductor Current IO(MAX) Maximum Output Current The inductor's resistance will factor into the overall efficiency of the converter. For best performances, the DC resistance should be less than 0.3 W for good efficiency.
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Table 3. List of Inductor
FDK TDK Taiyo Yuden Coil craft MIPW3226 Series VLF3010AT Series LQ CBL2012 DO1605-T Series LPO3010 TDK Taiyo Yuden
Table 4. List of Output Capacitor
Murata GRM188R60J475KE GRM21BR60J106ME19L GRM188R60OJ106ME JMK212BY475MG JMK212BJ106MG C2012X5ROJ475KB C1632X5ROJ475KT C2012X5ROJ106K 4.7 mF 10 mF 10 mF 4.7 mF 10 mF 4.7 mF 4.7 mF 10 mF
Output Capacitor Selection
Selecting the proper output capacitor is based on the desired output ripple voltage. Ceramic capacitors with low ESR values will have the lowest output ripple voltage and are strongly recommended. The output capacitor requires either an X7R or X5R dielectric. The output ripple voltage in PWM mode is given by:
DVOUT + DIL 4 1 fSW-3 COUT ) ESR (eq. 6)
Feed-Forward Capacitor Selection
In PFM mode (at light load), the output voltage is regulated by pulse frequency modulation. The output voltage ripple is independent of the output capacitor value. It is set by the threshold of PFM comparator.
The feed-forward capacitor sets the feedback loop response and is critical to obtain good loop stability. Given that the compensation is internally fixed, an 18 pF or higher ceramic capacitor is needed. Choose a small ceramic capacitor X7R or X5R or COG dielectric.
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APPLICATION BOARD
PCB Layout Recommendations
Good PCB layout plays an important role in switching mode power conversion. Careful PCB layout can help to minimize ground bounce, EMI noise and unwanted feedback that can affect the performance of the converter. Hints suggested below can be used as a guideline in most situations. 1. Use star-ground connection to connect the IC ground nodes and capacitor GND nodes together at one point. Keep them as close as possible, and then connect this to the ground plane through several vias. This will reduce noise in the ground plane by preventing the switching currents from flowing through the ground plane.
2. Place the power components (i.e., input capacitor, inductor and output capacitor) as close together as possible for best performance. All connecting traces must be short, direct, and wide to reduce voltage errors caused by resistive losses through the traces. 3. Separate the feedback path of the output voltage from the power path. Keep this path close to the NCP1522 circuit. And also route it away from noisy components. This will prevent noise from coupling into the voltage feedback trace. 4. Place the DC-DC converter away from noise sensitive circuitry, such as RF circuits. The following shows the NCP1522 demo board schematic, layout, and bill of materials:
VIN 1 CIN 2 OFF ON 3 GND EN FB 4 VIN LX 5
L COUT
VOUT
R1
Cff
R2
Figure 25. NCP1522 Board Schematic
Figure 26. NCP1522 Board Layout
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J1 1 2 U1 VFVIN VIN C1 4.7 mF 0 0 1 VP LX 5 LX 1 L1 2.2 mH 4 0 R2 220 R VP J5 EN J4 1 2 3 R3 220 K CON3 0 0 2 C2 4.7 mF VOUT R1 220 R C3 18 pF OUTPUT 1 2 J3
2 GND EN 3 EN NCP152x FB
Power
BNCH 0 0
Figure 27. Schematics
Figure 28. Silkscreen Layer
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Figure 29. Board Layout (Top View)
Figure 30. Board Layout (Bottom View)
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NCP1522
Bill of Materials
Item 1 2 3 4 5 6 7 8 Part Description NCP1522 DC-DC Converter 4.7 mF Ceramic Capacitor 6.3 V X5R 18 pF Ceramic Capacitor 50 V COG SMD Resistor 220 K SMD Inductor I/O Connector can be plugged by BLZ5.08/2 (Weidmuller reference) Jumper Header vertical mount 3*1, 2.54 mm Jumper Connector, 400 mils Ref U1 C1, C2 C3 R1, R2, R3 L1 J1, J3 J5 J6, J7 PCB Footprint TSOP-5 0805 0603 0805 1605 - - - Manufacturer On Semiconductor Murata Murata Vishay-Draloric Coilcraft Weidmuller Tyco Electronics/AMP Harwin Manufacturer Reference NCP1522 GRM21 Series GRM188 Series CRCW0805 DO1605 Series SL5.08/2/90B 5-826629-0 D3082-B01
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PACKAGE DIMENSIONS
TSOP-5 SN SUFFIX CASE 483-02 ISSUE F
NOTES: 1. DIMENSIONING AND TOLERANCING PER ASME Y14.5M, 1994. 2. CONTROLLING DIMENSION: MILLIMETERS. 3. MAXIMUM LEAD THICKNESS INCLUDES LEAD FINISH THICKNESS. MINIMUM LEAD THICKNESS IS THE MINIMUM THICKNESS OF BASE MATERIAL. 4. DIMENSIONS A AND B DO NOT INCLUDE MOLD FLASH, PROTRUSIONS, OR GATE BURRS. 5. OPTIONAL CONSTRUCTION: AN ADDITIONAL TRIMMED LEAD IS ALLOWED IN THIS LOCATION. TRIMMED LEAD NOT TO EXTEND MORE THAN 0.2 FROM BODY. DIM A B C D G H J K L M S MILLIMETERS MIN MAX 3.00 BSC 1.50 BSC 0.90 1.10 0.25 0.50 0.95 BSC 0.01 0.10 0.10 0.26 0.20 0.60 1.25 1.55 0_ 10 _ 2.50 3.00
NOTE 5 2X
D 5X 0.20 C A B
5 1 2 4 3
0.10 T 0.20 T L G A B S
M K
DETAIL Z
2X
DETAIL Z
J C 0.05 H T
SEATING PLANE
SOLDERING FOOTPRINT*
1.9 0.074
0.95 0.037
2.4 0.094 1.0 0.039 0.7 0.028
SCALE 10:1
mm inches
*For additional information on our Pb-Free strategy and soldering details, please download the ON Semiconductor Soldering and Mounting Techniques Reference Manual, SOLDERRM/D.
ON Semiconductor and are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. "Typical" parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including "Typicals" must be validated for each customer application by customer's technical experts. SCILLC does not convey any license under its patent rights nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.
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